Reference signal transmitting method and device in a multi-antenna system

ABSTRACT

Provided are a reference signal transmitting method and device in a multi-antenna system. A terminal generates a plurality of reference signal sequences to which different cyclic shift values are allocated, respectively, generates an orthogonal frequency division multiplexing (OFDM) symbol to which the plurality of reference signal sequences are mapped, and transmits the OFDM symbol to a base station through a plurality of antennas. Each cyclic shift value allocated to each reference signal sequence is determined on the basis of a parameter n indicated by a cyclic shift field transmitted from a physical downlink control channel (PDCCH).

CROSS-REFERENCE TO RELATED APPLICATIONS

This application claims the benefit of priority of U.S. Provisionalapplication No. 61/176,948 filed on May 11, 2009, and U.S. Provisionalapplication No. 61/178,027 filed on May 13, 2009, all of which areincorporated by reference in their entirety herein.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to wireless communication, and moreparticularly, to a method and apparatus for transmitting a referencesignal in a multi-antenna system.

2. Related Art

Effective transmission/reception methods and utilizations have beenproposed for a broadband wireless communication system to maximizeefficiency of radio resources. An orthogonal frequency divisionmultiplexing (OFDM) system capable of reducing inter-symbol interference(NI) with a low complexity is taken into consideration as one of nextgeneration wireless communication systems. In the OFDM, a serially inputdata symbol is converted into N parallel data symbols, and is thentransmitted by being carried on each of separated N subcarriers. Thesubcarriers maintain orthogonality in a frequency dimension. Eachorthogonal channel experiences mutually independent frequency selectivefading, and an interval of a transmitted symbol is increased, therebyminimizing inter-symbol interference.

When a system uses the OFDM as a modulation scheme, orthogonal frequencydivision multiple access (OFDMA) is a multiple access scheme in whichmultiple access is achieved by independently providing some of availablesubcarriers to a plurality of users. In the OFDMA, frequency resources(i.e., subcarriers) are provided to the respective users, and therespective frequency resources do not overlap with one another ingeneral since they are independently provided to the plurality of users.Consequently, the frequency resources are allocated to the respectiveusers in a mutually exclusive manner. In an OFDMA system, frequencydiversity for multiple users can be obtained by using frequencyselective scheduling, and subcarriers can be allocated variouslyaccording to a permutation rule for the subcarriers. In addition, aspatial multiplexing scheme using multiple antennas can be used toincrease efficiency of a spatial domain.

Meanwhile, in OFDM/OFDMA systems, a peak-to-average power ratio (PAPR)and a cubic metric (CM) may be increased. The PAPR means a ratio of amaximum transmission power and an average transmission power. Accordingto an increase of the PAPR, the capacity of a power amplifier must beincreased. It results from the fact that an OFDM symbol is theoverlapping of N sinusoidal signals on different subcarriers. To lowerthe PAPR acts as an important problem in a user equipment (UE) becauseit is necessary to reduce the capacity of the battery in the UE aspossible.

In order to lower the PAPR, a single carrier frequency division multipleaccess (SC-FDMA) scheme may be proposed. SC-FDMA is of a form in whichfrequency division multiple access (FDMA) is incorporated into a singlecarrier frequency division equalization (SC-FDE) scheme. SC-FDMA has asimilar characteristic to OFDMA in that data is modulated anddemodulated in the time domain and the frequency domain by using adiscrete Fourier transform (DFT), but is advantageous in reducingtransmission power because the PAPR of a transmission signal is low. Inparticular, SC-FDMA may be said to be suitable for uplink communicationfrom a UE, sensitive to transmission power, to a BS in relation to theuse of the battery. Furthermore, an SC-FDMA system makes small a changeof a signal and thus has a wide coverage as compared with other systemswhen the same power amplifier is used.

A multiple-in multiple-out (MIMO) technology can be used to improve theefficiency of data transmission and reception using multipletransmission antennas and multiple reception antennas. Schemes toimplement diversity in MIMO system includes a space frequency block code(SFBC), a space time block code (STBC), a cyclic delay diversity (CDD),a frequency switched transmit diversity (FSTD), a time switched transmitdiversity (TSTD), a precoding vector switching (PVS), a spatialmultiplexing (SM), and the like. An MIMO channel matrix according to thenumber of reception antennas and the number of transmission antennas canbe decomposed into a number of independent channels. Each of theindependent channels is called a layer or stream. The number of layersis called a rank.

In wireless communication systems, it is necessary to estimate an uplinkchannel or a downlink channel for the purpose of the transmission andreception of data, the acquisition of system synchronization, and thefeedback of channel information. In wireless communication systemenvironments, fading is generated because of multi-path time latency. Aprocess of restoring a transmit signal by compensating for thedistortion of the signal resulting from a sudden change in theenvironment due to such fading is referred to as channel estimation. Itis also necessary to measure the state of a channel for a cell to whicha user equipment belongs or other cells. To estimate a channel ormeasure the state of a channel, a reference signal (RS) which is knownto both a transmitter and a receiver can be used.

A subcarrier used to transmit the reference signal is referred to as areference signal subcarrier, and a subcarrier used to transmit data isreferred to as a data subcarrier. In an OFDM system, a method ofassigning the reference signal includes a method of assigning thereference signal to all the subcarriers and a method of assigning thereference signal between data subcarriers. The method of assigning thereference signal to all the subcarriers is performed using a signalincluding only the reference signal, such as a preamble signal, in orderto obtain the throughput of channel estimation. If this method is used,the performance of channel estimation can be improved as compared withthe method of assigning the reference signal between data subcarriersbecause the density of reference signals is in general high. However,since the amount of transmitted data is small in the method of assigningthe reference signal to all the subcarriers, the method of assigning thereference signal between data subcarriers is used in order to increasethe amount of transmitted data. If the method of assigning the referencesignal between data subcarriers is used, the performance of channelestimation can be deteriorated because the density of reference signalsis low. Accordingly, the reference signals should be properly arrangedin order to minimize such deterioration.

A receiver can estimate a channel by separating information about areference signal from a received signal because it knows the informationabout a reference signal and can accurately estimate data, transmittedby a transmit stage, by compensating for an estimated channel value.Assuming that the reference signal transmitted by the transmitter is p,channel information experienced by the reference signal duringtransmission is h, thermal noise occurring in the receiver is n, and thesignal received by the receiver is y, it can result in y=h·p+n. Here,since the receiver already knows the reference signal p, it can estimatea channel information value ĥ using Equation 1 in the case in which aLeast Square (LS) method is used.

ĥ=y/p=h+n/p=h+n  [Equation 1]

The accuracy of the channel estimation value ĥ estimated using thereference signal p is determined by the value {circumflex over (n)}. Toaccurately estimate the value h, the value {circumflex over (n)} mustconverge on 0. To this end, the influence of the value {circumflex over(n)}has to be minimized by estimating a channel using a large number ofreference signals. A variety of algorithms for a better channelestimation performance may exist.

Meanwhile, in a current LTE system, there have not yet been proposed amethod of transmitting a reference signal, which supports a MEMO systemusing a plurality of antennas in UL transmission, and a method ofallocating the cyclic shift values of a reference signal sequenceaccording to the above method. Accordingly, in MIMO systems, there is aneed for a method of transmitting a reference signal which guaranteesthe performance of channel estimation.

SUMMARY OF THE INVENTION

The present invention provides a method and apparatus for transmitting areference signal in a wireless communication system.

In an aspect, a method of transmitting a reference signal in amulti-antenna system is provided. The method includes generating aplurality of reference signal sequences to which different cyclic shiftvalues are respectively allocated, generating an orthogonal frequencydivision multiplexing (OFDM) symbol to which the plurality of referencesignal sequences is mapped, and transmitting the OFDM symbol to a basestation through a plurality of antennas, wherein the each cyclic shiftvalue allocated to each of the plurality of reference signal sequencesis determined based on a parameter n indicated by a cyclic shift fieldtransmitted through a physical downlink control channel (PDCCH). Each ofthe plurality of reference signal sequences may be a reference signalsequence for a different layer. The each cyclic shift value allocated toeach of the plurality of reference signal sequences may be determinedbased on a value indicated by a rank indicator (RI). The each cyclicshift value allocated to each of the plurality of reference signalsequences may be determined so that an interval between the cyclic shiftvalues becomes a maximum based on the parameter n. The each cyclic shiftvalue allocated to each of the plurality of reference signal sequencesmay be determined by a specific Equation. A number of layers may be oneof 2, 3, and 4. The each cyclic shift value allocated to each of theplurality of reference signal sequences may be determined at an intervalof an offset constantly fixed based on the parameter n. The each cyclicshift value allocated to each of the plurality of reference signalsequences may be transmitted by a higher layer based on the parameter n,and may be determined by an offset of a cyclic shift index correspondingto the parameter n in a one-to-one way. A number of the plurality ofantennas may be one of 2, 3, and 4. The OFDM symbol to which theplurality of reference signal sequences may be mapped is a fourth OFDMsymbol (OFDM symbol index 3) in a slot including 7 OFDM. The OFDM symbolto which the plurality of reference signal sequences may be mapped is athird OFDM symbol (OFDM symbol index 2) in a slot including 6 OFDM.

In another aspect, an apparatus for transmitting a reference signal in amulti-antenna system is provided. The apparatus includes a referencesignal generation unit configured for generating a plurality ofreference signal sequences to which different cyclic shift values arerespectively allocated, an orthogonal frequency division multiplexing(OFDM) symbol generation unit coupled to the reference signal generationunit and configured for generating an OFDM symbol to which the pluralityof reference signal sequences is mapped, and a radio frequency (RF) unitcoupled to the OFDM symbol generation unit and configured fortransmitting the OFDM symbol to a base station through a plurality ofantennas, wherein the each cyclic shift value allocated to each of theplurality of reference signal sequences is determined based on aparameter n indicated by a cyclic shift field transmitted through aphysical downlink control channel (PDCCH). The each cyclic shift valueallocated to each of the plurality of reference signal sequences may bedetermined based on a value indicated by a rank indicator (RI).

System performance can be improved because the multiplexing of areference signal is possible and robust frequency selective channelestimation is possible in a multi-antenna system.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 shows a wireless communication system.

FIG. 2 shows the structure of a radio frame in 3GPP LTE.

FIG. 3 shows an example of a resource grid of a single downlink slot.

FIG. 4 shows the structure of a downlink subframe.

FIG. 5 shows the structure of an uplink subframe.

FIG. 6 shows an example of the structure of a transmitter in an SC-FDMAsystem;

FIG. 7 shows an example of a scheme in which the subcarrier mapper mapsthe complex-valued symbols to the respective subcarriers of thefrequency domain;

FIG. 8 shows an example of the structure of a reference signaltransmitter for demodulation;

FIG. 9 shows examples of a subframe through which a reference signal istransmitted;

FIG. 10 shows an example of a transmitter using the clustered DFT-s OFDMtransmission scheme;

FIG. 11 shows another example of a transmitter using the clustered DFT-sOFDM transmission scheme;

FIG. 12 is yet another example of a transmitter using the clusteredDFT-s OFDM transmission scheme;

FIG. 13 shows an embodiment of a proposed method of transmitting areference signal; and

FIG. 14 is a block diagram of a UE in which the embodiments of thepresent invention are implemented.

DESCRIPTION OF EXEMPLARY EMBODIMENTS

The following technique may be used for various wireless communicationsystems such as code division multiple access (CDMA), a frequencydivision multiple access (FDMA), time division multiple access (TDMA),orthogonal frequency division multiple access (OFDMA), singlecarrier-frequency division multiple access (SC-FDMA), and the like. TheCDMA may be implemented as a radio technology such as universalterrestrial radio access (UTRA) or CDMA2000. The TDMA may be implementedas a radio technology such as a global system for mobile communications(GSM)/general packet radio service (GPRS)/enhanced data rtes for GSMevolution (EDGE). The OFDMA may be implemented by a radio technologysuch as IEEE (Institute of Electrical and Electronics Engineers) 802.11(Wi-Fi), IEEE 802.16 (WiMAX), IEEE 802.20, E-UTRA (Evolved UTRA), andthe like. IEEE 802.16m, an evolution of IEEE 802.16e, provides backwardcompatibility with a system based on IEEE 802.16e. The UTRA is part of auniversal mobile telecommunications system (UMTS). 3GPP (3^(rd)generation partnership project) LTE (long term evolution) is part of anevolved UMTS (E-UMTS) using the E-UTRA, which employs the OFDMA indownlink and the SC-FDMA in uplink. LTE-A (advanced) is an evolution of3GPP LTE.

Hereinafter, for clarification, LTE-A will be largely described, but thetechnical concept of the present invention is not meant to be limitedthereto.

FIG. 1 shows a wireless communication system.

The wireless communication system 10 includes at least one base station(BS) 11. Respective BSs 11 provide a communication service to particulargeographical areas 15 a, 15 b, and 15 c (which are generally calledcells). Each cell may be divided into a plurality of areas (which arecalled sectors). A user equipment (UE) 12 may be fixed or mobile and maybe referred to by other names such as MS (mobile station), MT (mobileterminal), UT (user terminal), SS (subscriber station), wireless device,PDA (personal digital assistant), wireless modem, handheld device. TheBS 11 generally refers to a fixed station that communicates with the UE12 and may be called by other names such as eNB (evolved-NodeB), BTS(base transceiver system), access point (AP), etc.

In general, a UE belongs to one cell, and the cell to which a TIEbelongs is called a serving cell. A BS providing a communication serviceto the serving cell is called a serving BS. The wireless communicationsystem is a cellular system, so a different cell adjacent to the servingcell exists. The different cell adjacent to the serving cell is called aneighbor cell. A BS providing a communication service to the neighborcell is called a neighbor BS. The serving cell and the neighbor cell arerelatively determined based on a UE.

This technique can be used for downlink or uplink. In general, downlinkrefers to communication from the BS 11 to the UE 12, and uplink refersto communication from the UE 12 to the BS 11. In downlink, a transmittermay be part of the BS 11 and a receiver may be part of the UE 12. Inuplink, a transmitter may be part of the UE 12 and a receiver may bepart of the BS 11.

The wireless communication system may be any one of a multiple-inputmultiple-output (MIMO) system, a multiple-input single-output (MISO)system, a single-input single-output (SISO) system, and a single-inputmultiple-output (SIMO) system. The MIMO system uses a plurality oftransmission antennas and a plurality of reception antennas. The MISOsystem uses a plurality of transmission antennas and a single receptionantenna. The SISO system uses a single transmission antenna and a singlereception antenna. The SIMO system uses a single transmission antennaand a plurality of reception antennas.

Hereinafter, a transmission antenna refers to a physical or logicalantenna used for transmitting a signal or a stream, and a receptionantenna refers to a physical or logical antenna used for receiving asignal or a stream.

FIG. 2 shows the structure of a radio frame in 3GPP LTE. It may bereferred to Paragraph 5 of “Technical Specification Group Radio AccessNetwork; Evolved Universal Terrestrial Radio Access (E-UTRA); Physicalchannels and modulation (Release 8)” to 3GPP (3rd generation partnershipproject) TS 36.211 V8.2.0 (2008-03).

Referring to FIG. 2, the radio frame includes 10 subframes, and onesubframe includes two slots. The slots in the radio frame are numberedby #0 to #19. A time taken for transmitting one subframe is called atransmission time interval (TTI). The TTI may be a scheduling unit for adata transmission. For example, a radio frame may have a length of 10ms, a subframe may have a length of 1 ms, and a slot may have a lengthof 0.5 ms.

One slot includes a plurality of orthogonal frequency divisionmultiplexing (OFDM) symbols in a time domain and a plurality ofsubcarriers in a frequency domain. Since 3GPP LTE uses OFDMA indownlink, the OFDM symbols are used to express a symbol period. The OFDMsymbols may be called by other names depending on a multiple-accessscheme. For example, when a single carrier frequency division multipleaccess (SC-FDMA) is in use as an uplink multi-access scheme, the OFDMsymbols may be called SC-FDMA symbols. A resource block (RB), a resourceallocation unit, includes a plurality of continuous subcarriers in aslot. The structure of the radio frame is merely an example. Namely, thenumber of subframes included in a radio frame, the number of slotsincluded in a subframe, or the number of OFDM symbols included in a slotmay vary.

3GPP LTE defines that one slot includes seven OFDM symbols in a normalcyclic prefix (CP) and one slot includes six OFDM symbols in an extendedCP.

FIG. 3 shows an example of a resource grid of a single downlink slot.

A downlink slot includes a plurality of OFDM symbols in the time domainand N_(RB) number of resource blocks (RBs) in the frequency domain. TheN_(RB) number of resource blocks included in the downlink slot isdependent upon a downlink transmission bandwidth set in a cell. Forexample, in an LTE system, N_(RB) may be any one of 60 to 110. Oneresource block includes a plurality of subcarriers in the frequencydomain. An uplink slot may have the same structure as that of thedownlink slot.

Each element on the resource grid is called a resource element. Theresource elements on the resource grid can be discriminated by a pair ofindexes (k,l) in the slot. Here, k (k=0, . . . , N_(RB)×12−1) is asubcarrier index in the frequency domain, and 1 is an OFDM symbol indexin the time domain.

Here, it is illustrated that one resource block includes 7×12 resourceelements made up of seven OFDM symbols in the time domain and twelvesubcarriers in the frequency domain, but the number of OFDM symbols andthe number of subcarriers in the resource block are not limited thereto.The number of OFDM symbols and the number of subcarriers may varydepending on the length of a cyclic prefix (CP), frequency spacing, andthe like. For example, in case of a normal CP, the number of OFDMsymbols is 7, and in case of an extended CP, the number of OFDM symbolsis 6. One of 128, 256, 512, 1024, 1536, and 2048 may be selectively usedas the number of subcarriers in one OFDM symbol.

FIG. 4 shows the structure of a downlink subframe.

A downlink subframe includes two slots in the time domain, and each ofthe slots includes seven OFDM symbols in the normal CP. First three OFDMsymbols (maximum four OFDM symbols with respect to a 1.4 MHz bandwidth)of a first slot in the subframe corresponds to a control region to whichcontrol channels are allocated, and the other remaining OFDM symbolscorrespond to a data region to which a physical downlink shared channel(PDSCH) is allocated. Down link control channels used in the 3GPP LTEinclude a physical control format indicator channel (PCFICH), a physicaldownlink control channel (PDCCH), a physical hybrid-ARQ indicatorchannel (PHICH), and so on. The PCFICH transmitted in the first OFDMsymbol of a subframe carries information about the number of OFDMsymbols (that is, the size of a control region) which is used totransmit control channels within the subframe. The PHICH carries anacknowledgement (ACK)/non-acknowledgement (NACK) signal for an uplinkhybrid automatic repeat request (HARQ). In other words, an ACK/NACKsignal for uplink data transmitted by a user equipment is transmitted onthe PHICH. Control information transmitted through the PDCCH is calleddownlink control information (DCI). The DCI indicates uplink or downlinkscheduling information, an uplink transmission power control command forspecific user equipment groups, etc. Especially, a DCI format 0 amongDCIs may be used for scheduling of a physical uplink shared channel(PUSCH).

FIG. 5 shows the structure of an uplink subframe.

An uplink subframe may be divided into a control region and a dataregion in the frequency domain. A physical uplink control channel(PUCCH) for transmitting uplink control information is allocated to thecontrol region. A physical uplink shared channel (PUSCH) fortransmitting data is allocated to the data region. The user equipmentdoes not transmit the PUCCH and the PUSCH simultaneously to maintain asingle carrier property.

The PUCCH with respect to a UE is allocated by a pair of resource blocksin a subframe. The resource blocks belonging to the pair of resourceblocks (RBs) occupy different subcarriers in first and second slots,respectively. The frequency occupied by the RBs belonging to the pair ofRBs is changed based on a slot boundary. This is said that the pair ofRBs allocated to the PUCCH are frequency-hopped at the slot boundary.The UE can obtain a frequency diversity gain by transmitting uplinkcontrol information through different subcarriers according to time. InFIG. 5, m is a position index indicating the logical frequency domainpositions of the pair of RBs allocated to the PUCCH in the subframe.

Uplink control information transmitted on the PUCCH may include a HARQACK/NACK, a channel quality indicator (CQI) indicating the state of adownlink channel, a scheduling request (SR), and the like.

The PUSCH is mapped to a uplink shared channel (UL-SCH), a transportchannel. Uplink data transmitted on the PUSCH may be a transport block,a data block for the UL-SCH transmitted during the TTI. The transportblock may be user information. Or, the uplink data may be multiplexeddata. The multiplexed data may be data obtained by multiplexing thetransport block for the UL-SCH and control information. For example,control information multiplexed to data may include a CQI, a precodingmatrix indicator (PMI), an HARQ, a rank indicator (RI), or the like. Orthe uplink data may include only control information.

In an LTE-A system, UL adopts an SC-FDMA transmission scheme. Atransmission scheme in which IFFT is performed after DFT spreading iscalled SC-FDMA. SC-FDMA may also be called a discrete Fourier transformspread (DFT-s) OFDM. In SC-FDMA, the peak-to-average power ratio (PAPR)or a cubic metric (CM) may be lowered. If the SC-FDMA transmissionscheme is used, transmission power efficiency in a UE having limitedpower consumption may be increased because the non-linear distortionperiod of a power amplifier may be avoided. Consequently, userthroughput may be increased.

FIG. 6 shows an example of the structure of a transmitter in an SC-FDMAsystem.

Referring to FIG. 6, the transmitter 50 includes a discrete Fouriertransform (DFT) unit 51, a subcarrier mapper 52, an inverse fast Fouriertransform (IFFT) unit 53, and a cyclic prefix (CP) insertion unit 54.The transmitter 50 may include a scramble unit (not shown), a modulationmapper (not shown), a layer mapper (not shown), and a layer permutator(not shown), which may be placed in front of the DFT unit 51.

The DFT unit 51 outputs complex-valued symbols by performing DFT oninput symbols. For example, when N_(tx) symbols are input (where N is anatural number), a DFT size is N_(tx). The DFT unit 51 may be called atransform precoder. The subcarrier mapper 52 maps the complex-valuedsymbols to the respective subcarriers of the frequency domain. Thecomplex-valued symbols may be mapped to resource elements correspondingto a resource block allocated for data transmission. The subcarriermapper 52 may be called a resource element mapper. The IFFT unit 53outputs a baseband signal for data (that is, a time domain signal) byperforming IFFT on the input symbols. The CP insertion unit 54 copiessome of the rear part of the baseband signal for data and inserts thecopied parts into the former part of the baseband signal for data.Orthogonality may be maintained even in a multi-path channel becauseinter-symbol interference (ISI) and inter-carrier interference (ICI) areprevented through CP insertion.

FIG. 7 shows an example of a scheme in which the subcarrier mapper mapsthe complex-valued symbols to the respective subcarriers of thefrequency domain. Referring to FIG. 7( a), the subcarrier mapper mapsthe complex-valued symbols, outputted from the DFT unit, to subcarrierscontiguous to each other in the frequency domain. ‘0’ is inserted intosubcarriers to which the complex-valued symbols are not mapped. This iscalled localized mapping. In a 3GPP LTE system, a localized mappingscheme is used. Referring to FIG. 7( b), the subcarrier mapper insertsan (L−1) number of ‘0’ every two contiguous complex-valued symbols whichare outputted from the DFT unit (L is a natural number). That is, thecomplex-valued symbols outputted from the DFT unit are mapped tosubcarriers distributed at equal intervals in the frequency domain. Thisis called distributed mapping. If the subcarrier mapper uses thelocalized mapping scheme as in FIG. 7( a) or the distributed mappingscheme as in FIG. 7( b), a single carrier characteristic is maintained.

FIG. 8 shows an example of the structure of a reference signaltransmitter for demodulation.

Referring to FIG. 8 the reference signal transmitter 60 includes asubcarrier mapper 61, an IFFT unit 62, and a CP insertion unit 63.Unlike the transmitter 50 of FIG. 6, in the reference signal transmitter60, a reference signal is directly generated in the frequency domainwithout passing through the DFT unit 51 and then mapped to subcarriersthrough the subcarrier mapper 61. Here, the subcarrier mapper may mapthe reference signal to the subcarriers using the localized mappingscheme of FIG. 7( a).

FIG. 9 shows examples of a subframe through which a reference signal istransmitted. The structure of the subframe in FIG. 9( a) shows a case ofa normal CP. The subframe includes a first slot and a second slot. Eachof the first slot and the second slot includes 7 OFDM symbols. The 14OFDM symbols within the subframe are assigned respective symbol indices0 to 13. A reference signal may be transmitted through the OFDM symbolshaving the symbol indices 3 and 10. Data may be transmitted through theremaining OFDM symbols other than the OFDM symbols through which thereference signal is transmitted. The structure of a subframe in FIG. 9(b) shows a case of an extended CP. The subframe includes a first slotand a second slot. Each of the first slot and the second slot includes 6OFDM symbols. The 12 OFDM symbols within the subframe are assignedsymbol indices 0 to 11. A reference signal is transmitted through theOFDM symbols having the symbol indices 2 and 8. Data is transmittedthrough the remaining OFDM symbols other than the OFDM symbols throughwhich the reference signal is transmitted.

Although not shown in FIG. 9, a sounding reference signal (SRS) may betransmitted through the OFDM symbols within the subframe. The SRS is areference signal for UL scheduling which is transmitted from a UE to aBS. The BS estimates a UL channel through the received SRS and uses theestimated UL channel in UL scheduling.

A clustered DFT-s OFDM transmission scheme is a modification of theexisting SC-FDMA transmission scheme and is a method of dividing datasymbols, subjected to a precoder, into a plurality of subblocks,separating the subblocks, and mapping the subblocks in the frequencydomain.

FIG. 10 shows an example of a transmitter using the clustered DFT-s OFDMtransmission scheme. Referring to FIG. 10, the transmitter 70 includes aDFT unit 71, a subcarrier mapper 72, an IFFT unit 73, and a CP insertionunit 74. The transmitter 70 may further include a scramble unit (notshown), a modulation mapper (not shown), a layer mapper (not shown), anda layer permutator (not shown), which may be placed in front of the DFTunit 71.

Complex-valued symbols outputted from the DFT unit 71 are divided into Nsubblocks (N is a natural number). The N subblocks may be represented bya subblock #1, a subblock #2, . . . , a subblock #N. The subcarriermapper 72 distributes the N subblocks in the frequency domain and mapsthe N subblocks to subcarriers. The NULL may be inserted every twocontiguous subblocks. The complex-valued symbols within one subblock maybe mapped to subcarriers contiguous to each other in the frequencydomain. That is, the localized mapping scheme may be used within onesubblock.

The transmitter 70 of FIG. 10 may be used both in a single carriertransmitter or a multi-carrier transmitter. If the transmitter 70 isused in the single carrier transmitter, all the N subblocks correspondto one carrier. If the transmitter 70 is used in the multi-carriertransmitter, each of the N subblocks may correspond to one carrier.Alternatively, even if the transmitter 70 is used in the multi-carriertransmitter, a plurality of subblocks of the N subblocks may correspondto one carrier. Meanwhile, in the transmitter 70 of FIG. 10, a timedomain signal is generated through one IFFT unit 73. Accordingly, inorder for the transmitter 70 of FIG. 10 to be used in a multi-carriertransmitter, subcarrier intervals between contiguous carriers in acontiguous carrier allocation situation must be aligned.

FIG. 11 shows another example of a transmitter using the clustered DFT-sOFDM transmission scheme. Referring to FIG. 11, the transmitter 80includes a DFT unit 81, a subcarrier mapper 82, a plurality of IFFTunits 83-1, 83-2, . . . , 83-N (N is a natural number), and a CPinsertion unit 84. The transmitter 80 may further include a scrambleunit (not shown), a modulation mapper (not shown), a layer mapper (notshown), and a layer permutator (not shown), which may be placed in frontof the DFT unit 71.

IFFT is individually performed on each of N subblocks. An n^(th) IFFTunit 83-n outputs an n^(th) baseband signal (n=1, 2, . . . , N) byperforming IFFT on a subblock #n. The n^(th) baseband signal ismultiplied by an n^(th) carrier signal to produce an n^(th) radiosignal. After the N radio signals generated from the N subblocks areadded, a CP is inserted by the CP insertion unit 84. The transmitter 80of FIG. 11 may be used in a discontinuous carrier allocation situationwhere carriers allocated to the transmitter are not contiguous to eachother.

FIG. 12 is yet another example of a transmitter using the clusteredDFT-s OFDM transmission scheme. FIG. 12 is a chunk-specific DFT-s OFDMsystem performing DFT precoding on a chunk basis. This may be called NxSC-FDMA. Referring to FIG. 12, the transmitter 90 includes a code blockdivision unit 91, a chunk division unit 92, a plurality of channelcoding units 93-1, . . . , 93-N, a plurality of modulators 94-1, . . . ,94-N, a plurality of DFT units 95-1, . . . , 95-N, a plurality ofsubcarrier mappers 96-1, . . . , 96-N, a plurality of IFFT units 97-1, .. . , 97-N, and a CP insertion unit 98. Here, N may be the number ofmultiple carriers used by a multi-carrier transmitter. Each of thechannel coding units 93-1, . . . , 93-N may include a scramble unit (notshown). The modulators 94-1, . . . , 94-N may also be called modulationmappers. The transmitter 90 may further include a layer mapper (notshown) and a layer permutator (not shown) which may be placed in frontof the DFT units 95-1, . . . , 95-N.

The code block division unit 91 divides a transmission block into aplurality of code blocks. The chunk division unit 92 divides the codeblocks into a plurality of chunks. Here, the code block may be datatransmitted by a multi-carrier transmitter, and the chunk may be a datapiece transmitted through one of multiple carriers. The transmitter 90performs DFT on a chunk basis. The transmitter 90 may be used in adiscontinuous carrier allocation situation or a contiguous carrierallocation situation.

A UL reference signal is described below.

In general, the reference signal is transmitted in the form of asequence. A specific sequence may be used as the reference signalsequence without a special limit. A phase shift keying (PSK)-basedcomputer generated sequence may be used as the reference signalsequence. Examples of PSK include binary phase shift keying (BPSK) andquadrature phase shift keying (QPSK). Alternatively, a constantamplitude zero auto-correlation (CAZAC) sequence may be used as thereference signal sequence. Examples of the CAZAC sequence include aZadoff-Chu (ZC)-based sequence, a ZC sequence with cyclic extension, anda ZC sequence with truncation. Alternatively, a pseudo-random (PN)sequence may be used as the reference signal sequence. Examples of thePN sequence include an m-sequence, a computer-generated sequence, a goldsequence, and a Kasami sequence. A cyclically shifted sequence may beused as the reference signal sequence.

A UL reference signal may be divided into a demodulation referencesignal (DMRS) and a sounding reference signal (SRS). The DMRS is areference signal used in channel estimation for the demodulation of areceived signal. The DMRS may be associated with the transmission of aPUSCH or PUCCH. The SRS is a reference signal transmitted from a UE to aBS for UL scheduling. The BS estimates an UL channel through thereceived SRS and uses the estimated UL channel in UL scheduling. The SRSis not associated with the transmission of a PUSCH or PUCCH. The samekind of a basic sequence may be used for the DMRS and the SRS.Meanwhile, in UL multi-antenna transmission, precoding applied to theDMRS may be the same as precoding applied to a PUSCH. Cyclic shiftseparation is a primary scheme for multiplexing the DMRS. In an LTE-Asystem, the SRS may not be precoded and may be an antenna-specificreference signal.

A reference signal sequence r_(u) ^((α))(n) may be defined based on abasic sequence b_(u,v)(n) and a cyclic shift α according to Equation 2.

r _(u,v) ^((α))(n)=e ^(jαn) b _(u,v)(n),0≦n<M _(sc) ^(RS)

In Equation 2, M_(sc) ^(RS)(1≦m≦N_(RB) ^(max,UL)) is the length of thereference signal sequence and M_(sc) ^(RS)=m*N_(sc) ^(RB). N_(sc) ^(RB)is the size of a resource block indicated by the number of subcarriersin the frequency domain. N_(RB) ^(max,UL) indicates a maximum value of aUL bandwidth indicated by a multiple of N_(sc) ^(RB). A plurality ofreference signal sequences may be defined by differently applying acyclic shift value α from one basic sequence.

A basic sequence b_(u,v)(n) is divided into a plurality of groups. Here,u□{0, 1, . . . , 29} indicates a group index, and v indicates a basicsequence index within the group. The basic sequence depends on thelength M_(sc) ^(RS) of the basic sequence. Each group includes a basicsequence (v=0) having a length of M_(sc) ^(RS) for m (1≦m≦5) andincludes 2 basic sequences (v=0, 1) having a length of M_(sc) ^(RS) form (6≦m≦n_(RB) ^(max,UL)). The sequence group index u and the basicsequence index v within a group may vary according to time as in grouphopping or sequence hopping.

Furthermore, if the length of the reference signal sequence is 3N_(sc)^(RB) or higher, the basic sequence may be defined by Equation 3.

b _(u,v)(n)=(n mod N _(ZC) ^(RS)),0≦n<M _(sc) ^(RS)

In Equation 3, q indicates a root index of a Zadoff-Chu (ZC) sequence.N_(ZC) ^(RS) is the length of the ZC sequence and may be a maximum primenumber smaller than M_(sc)RS. The ZC sequence having the root index qmay be defined by Equation 4.

${{x_{q}(m)} = ^{{- j}\frac{\pi \; q\; {m{({m + 1})}}}{N_{ZC}^{RS}}}},\mspace{14mu} {0 \leq m \leq {N_{ZC}^{RS} - 1}}$

q may be given by Equation 5.

q=└ q+ ½┘+v·(−1)^(└2 q┘)

q=N _(ZC) ^(RS)·(u+1)/31

If the length of the reference signal sequence is 3N_(sc) ^(RB) or less,the basic sequence may be defined by Equation 6.

b _(u,v)(n)=e^(jφ(n)π/4),0≦n≦M _(sc) ^(RS)−1

Table 1 is an example where φ(n) is defined when M_(sc) ^(RS)=N_(sc)^(RB).

φ(0), . . . , φ(11) 0 −1 1 3 −3 3 3 1 1 3 1 −3 3 1 1 1 3 3 3 −1 1 −3 −31 −3 3 2 1 1 −3 −3 −3 −1 −3 −3 1 −3 1 −1 3 −1 1 1 1 1 −1 −3 −3 1 −3 3 −14 −1 3 1 −1 1 −1 −3 −1 1 −1 1 3 5 1 −3 3 −1 −1 1 1 −1 −1 3 −3 1 6 −1 3−3 −3 −3 3 1 −1 3 3 −3 1 7 −3 −1 −1 −1 1 −3 3 −1 1 −3 3 1 8 1 −3 3 1 −1−1 −1 1 1 3 −1 1 9 1 −3 −1 3 3 −1 −3 1 1 1 1 1 10 −1 3 −1 1 1 −3 −3 −1−3 −3 3 −1 11 3 1 −1 −1 3 3 −3 1 3 1 3 3 12 1 −3 1 1 −3 1 1 1 −3 −3 −3 113 3 3 −3 3 −3 1 1 3 −1 −3 3 3 14 −3 1 −1 −3 −1 3 1 3 3 3 −1 1 15 3 −1 1−3 −1 −1 1 1 3 1 −1 −3 16 1 3 1 −1 1 3 3 3 −1 −1 3 −1 17 −3 1 1 3 −3 3−3 −3 3 1 3 −1 18 −3 3 1 1 −3 1 −3 −3 −1 −1 1 −3 19 −1 3 1 3 1 −1 −1 3−3 −1 −3 −1 20 −1 −3 1 1 1 1 3 1 −1 1 −3 −1 21 −1 3 −1 1 −3 −3 −3 −3 −31 −1 −3 22 1 1 −3 −3 −3 −3 −1 3 −3 1 −3 3 23 1 1 −1 −3 −1 −3 1 −1 1 3 −11 24 1 1 3 1 3 3 −1 1 −1 −3 −3 1 25 1 −3 3 3 1 3 3 1 −3 −1 −1 3 26 1 3−3 −3 3 −3 1 −1 −1 3 −1 −3 27 −3 −1 −3 −1 −3 3 1 −1 1 3 −3 −3 28 −1 3 −33 −1 3 3 −3 3 3 −1 −1 29 3 −3 −3 −1 −1 −3 −1 3 −3 3 1 −1

Table 2 is an example where φ(n) is defined when M_(sc) ^(RS)=2*N_(sc)^(RB).

φ(0), . . . , φ(23) 0 −1 3 1 −3 3 −1 1 3 −3 3 1 3 −3 3 1 1 −1 1 3 −3 3−3 −1 −3 1 −3 3 −3 −3 −3 1 −3 −3 3 −1 1 1 1 3 1 −1 3 −3 −3 1 3 1 1 −3 23 −1 3 3 1 1 −3 3 3 3 3 1 −1 3 −1 1 1 −1 −3 −1 −1 1 3 3 3 −1 −3 1 1 3 −31 1 −3 −1 −1 1 3 1 3 1 −1 3 1 1 −3 −1 −3 −1 4 −1 −1 −1 −3 −3 −1 1 1 3 3−1 3 −1 1 −1 −3 1 −1 −3 −3 1 −3 −1 −1 5 −3 1 1 3 −1 1 3 1 −3 1 −3 1 1 −1−1 3 −1 −3 3 −3 −3 −3 1 1 6 1 1 −1 −1 3 −3 −3 3 −3 1 −1 −1 1 −1 1 1 −1−3 −1 1 −1 3 −1 −3 7 −3 3 3 −1 −1 −3 −1 3 1 3 1 3 1 1 −1 3 1 −1 1 3 −3−1 −1 1 8 −3 1 3 −3 1 −1 −3 3 −3 3 −1 −1 −1 −1 1 −3 −3 −3 1 −3 −3 −3 1−3 9 1 1 −3 3 3 −1 −3 −1 3 −3 3 3 3 −1 1 1 −3 1 −1 1 1 −3 1 1 10 −1 1 −3−3 3 −1 3 −1 −1 −3 −3 −3 −1 −3 −3 1 −1 1 3 3 −1 1 −1 3 11 1 3 3 −3 −3 13 1 −1 −3 −3 −3 3 3 −3 3 3 −1 −3 3 −1 1 −3 1 12 1 3 3 1 1 1 −1 −1 1 −3 3−1 1 1 −3 3 3 −1 −3 3 −3 −1 −3 −1 13 3 −1 −1 −1 −1 −3 −1 3 3 1 −1 1 3 33 −1 1 1 −3 1 3 −1 −3 3 14 −3 −3 3 1 3 1 −3 3 1 3 1 1 3 3 −1 −1 −3 1 −3−1 3 1 1 3 15 −1 −1 1 −3 1 3 −3 1 −1 −3 −1 3 1 3 1 −1 −3 −3 −1 −1 −3 −3−3 −1 16 −1 −3 3 −1 −1 −1 −1 1 1 −3 3 1 3 3 1 −1 1 −3 1 −3 1 1 −3 −1 171 3 −1 3 3 −1 −3 1 −1 −3 3 3 3 −1 1 1 3 −1 −3 −1 3 −1 −1 −1 18 1 1 1 1 1−1 3 −1 −3 1 1 3 −3 1 −3 −1 1 1 −3 −3 3 1 1 −3 19 1 3 3 1 −1 −3 3 −1 3 33 −3 1 −1 1 −1 −3 −1 1 3 −1 3 −3 −3 20 −1 −3 3 −3 −3 −3 −1 −1 −3 −1 −3 31 3 −3 −1 3 −1 1 −1 3 −3 1 −1 21 −3 −3 1 1 −1 1 −1 1 −1 3 1 −3 −1 1 −1 1−1 −1 3 3 −3 −1 1 −3 22 −3 −1 −3 3 1 −1 −3 −1 −3 −3 3 −3 3 −3 −1 1 3 1−3 1 3 3 −1 −3 23 −1 −1 −1 −1 3 3 3 1 3 3 −3 1 3 −1 3 −1 3 3 −3 3 1 −1 33 24 1 −1 3 3 −1 −3 3 −3 −1 −1 3 −1 3 −1 −1 1 1 1 1 −1 −1 −3 −1 3 25 1−1 1 −1 3 −1 3 1 1 −1 −1 −3 1 1 −3 1 3 −3 1 1 −3 −3 −1 −1 26 −3 −1 1 3 11 −3 −1 −1 −3 3 −3 3 1 −3 3 −3 1 −1 1 −3 1 1 1 27 −1 −3 3 3 1 1 3 −1 −3−1 −1 −1 3 1 −3 −3 −1 3 −3 −1 −3 −1 −3 −1 28 −1 −3 −1 −1 1 −3 −1 −1 1 −1−3 1 1 −3 1 −3 −3 3 1 1 −1 3 −1 −1 29 1 1 −1 −1 −3 −1 3 −1 3 −1 1 3 1 −13 1 3 −3 −3 1 −1 −1 1 3

Hopping of a reference signal may be applied as follows.

The sequence group index u of a slot index n_(s) may be defined based ona group hopping pattern f_(gh)(n_(s)) and a sequence shift patternf_(ss) according to Equation 7.

u=(f _(gh)(n _(s))+f _(SS)) mod 30

17 different group hopping patterns and 30 different sequence shiftpatterns may exist. Whether to apply group hopping may be indicated by ahigher layer.

A PUCCH and a PUSCH may have the same group hopping pattern. A grouphopping pattern f_(gh)(n_(s)) may be defined by Equation 8.

${f_{gh}( n_{s} )} = \{ \begin{matrix}0 & {{if}\mspace{14mu} {group}\mspace{14mu} {hopping}\mspace{14mu} {is}\mspace{14mu} {disabled}} \\{( {\sum\limits_{i = 0}^{7}{{c( {{8n_{s}} + i} )} \cdot 2^{i}}} ){mod}\; 30} & {{if}\mspace{14mu} {group}\mspace{14mu} {hopping}\mspace{14mu} {is}\mspace{14mu} {enabled}}\end{matrix} $

In Equation 8, c(i) is a pseudo random sequence that is a PN sequenceand may be defined by a Gold sequence of a length−31. Equation 9 showsan example of a gold sequence c(n).

c(n)=(x ₁(n+N _(c))+x ₂(n+N _(c))) mod 2

x ₁(n+31)=(x ₁(n+3)+x ₁(n)) mod 2

x ₂(n+31)=(x ₂(n+3)+x ₂(n+2)+x ₁(n+1)+x ₁(n)) mod 2

Here, Nc=1600, x₁(i) is a first m-sequence, and x₂(i) is a secondm-sequence. For example, the first m-sequence or the second m-sequencemay be initialized according to a cell identifier (ID) for every OFDMsymbol, a slot number within one radio frame, an OFDM symbol indexwithin a slot, and the type of a CP. A pseudo random sequence generatormay be initialized to

$c_{init} = \lfloor \frac{N_{ID}^{cell}}{30} \rfloor$

in the first of each radio frame.

A PUCCH and a PUSCH may have the same sequence shift pattern. Thesequence shift pattern of the PUCCH may be f_(ss) ^(PUCCH)=N_(ID)^(cell) mod 30. The sequence shift pattern of the PUSCH may be f_(ss)^(PUCCH)=(f_(ss) ^(PUCCH)+Δ_(ss)) mod 30 and Δ_(ss)□{0, 1, . . . , 29}may be configured by a higher layer.

Sequence hopping may be applied to only a reference signal sequencehaving a length longer than 6N_(sc) ^(RB). Here, a basic sequence indexv within a basic sequence group of a slot index II, may be defined byEquation 10.

$v = \{ \begin{matrix}{c( n_{s} )} & {{if}\mspace{14mu} {group}\mspace{14mu} {hopping}\mspace{14mu} {is}\mspace{14mu} {disabled}\mspace{14mu} {and}\mspace{14mu} {sequence}\mspace{14mu} {hopping}\mspace{14mu} {is}\mspace{14mu} {enabled}} \\0 & {otherwise}\end{matrix} $

c(i) may be represented by an example of Equation 9. Whether to applysequence hopping may be indicated by a higher layer. A pseudo randomsequence generator may be initialized to

$c_{init} = {{\lfloor \frac{N_{ID}^{cell}}{30} \rfloor \cdot 2^{5}} + f_{ss}^{PUSCH}}$

in the first of each radio frame.

A DMRS sequence for a PUSCH may be defined by Equation 11.

r ^(PUSCH)(m·M _(sc) ^(RS) +n)=r _(u,v) ^((α))(n)

In Equation 11, m=0, 1, . . . and n=0, . . . , M_(sc) ^(RS)−1. M_(sc)^(RS)=M_(sc) ^(PUSCH).

α=2πn_(cs)/12, that is, a cyclic shift value is given within a slot, andn_(cs) may be defined by Equation 12.

n _(cs)=(n _(DMRS) ⁽¹⁾ +n _(DMRS) ⁽²⁾ +n _(PRS)(n _(s))) mod 12

In Equation 12, n_(DMRS) ⁽¹⁾ is indicated by a parameter transmitted bya higher layer, and Table 3 shows an example of a correspondingrelationship between the parameter and n_(DMRS) ⁽¹⁾.

Parameter n_(DMRS) ⁽¹⁾ 0 0 1 2 2 3 3 4 4 6 5 8 6 9 7 10

Back in Equation 12, n_(DMRS) ⁽²⁾ may be defined by a cyclic shift fieldwithin a DCI format 0 for a transmission block corresponding to PUSCHtransmission. The DCI format is transmitted in a PDCCH. The cyclic shiftfield may have a length of 3 bits.

Table 4 shows an example of a corresponding relationship between thecyclic shift field and n_(DMRS) ⁽²⁾.

Cyclic shift field in DCI format 0 n_(DMRS) ⁽²⁾ 000 0 001 6 010 3 011 4100 2 101 8 110 10 111 9

Table 5 is another example of a corresponding relationship between thecyclic shift field and n_(DMRS) ⁽²⁾.

Cyclic shift field in DCI format 0 n_(DMRS) ⁽²⁾ 000 0 001 2 010 3 011 4100 6 101 8 110 9 111 10

If a PDCCH including the DCI format 0 is not transmitted in the sametransmission block, if the first PUSCH is semi-persistently scheduled inthe same transmission block, or if the first PUSCH is scheduled by arandom access response grant in the same transmission block, n_(DMRS)⁽²⁾ may be 0.

n_(PRS)(n_(s)) may be defined by Equation 13.

n _(PRS)(n _(s))=Σ_(i=0) ⁷ c(8N _(symb) ^(UL) ·n _(s) +i)·2^(i)

c(i) may be represented by the example of Equation 9 and may be appliedin a cell-specific way of c(i). A pseudo random sequence generator maybe initialized to

$c_{init} = {{\lfloor \frac{N_{ID}^{cell}}{30} \rfloor \cdot 2^{5}} + f_{ss}^{PUSCH}}$

in the first of each radio frame.

A DMRS sequence r^(PUSCH) is multiplied by an amplitude scaling factorβ_(PUSCH) and mapped to a physical transmission block, used in relevantPUSCH transmission, from r^(PUSCH)(0) in a sequence starting. The DIVERSsequence is mapped to a fourth OFDM symbol (OFDM symbol index 3) in caseof a normal CP within one slot and mapped to a third OFDM symbol (OFDMsymbol index 2) within one slot in case of an extended CP.

An SRS sequence r_(SRS)(n)=r_(u,v) ^((α)) is defined. u indicates aPUCCH sequence group index, and v indicates a basic sequence index. Thecyclic shift value α is defined by Equation 14.

$\alpha = {2\pi \frac{n_{SRS}^{cs}}{8}}$

n_(SRS) ^(cs) is a value configured by a higher layer in related to eachUE and may be any one of integers from 0 to 7.

A proposed method of transmitting a reference signal is described below.

In a current LTE system, there have not yet been proposed a method oftransmitting a reference signal, which supports a MIMO system using aplurality of antennas in UL transmission, and a method of allocating thecyclic shift values of a reference signal sequence using the method.Accordingly, the present invention proposes a method of transmitting areference signal and a method of allocating cyclic shift values whichguarantee the performance of channel estimation in an MIMO system. Thepresent invention may be applied to OFDM, SC-FDMA, and clustered DFT-sOFDM systems and also to other types of systems. Furthermore, an examplewhere the proposed method of transmitting a reference signal is appliedto a UL reference signal is described, but not limited thereto. Theproposed method may also be applied to a DL reference signal.Furthermore, the proposed method is not limited to whether precoding isperformed.

FIG. 13 shows an embodiment of the proposed method of transmitting areference signal.

At step S100, a UE generates a plurality of reference signal sequencesto which different cyclic shift values are allocated. At step S110, theUE generates OFDM symbols to which the plurality of reference signalsequences is mapped. At step S120, the UE transmits the OFDM symbols toa BS through a plurality of antennas.

A variety of methods may be used to allocate the different cyclic shiftvalues to the plurality of reference signal sequences. It is assumedthat the reference signal is a DMRS.

First, a method of continuously allocating the cyclic shift values of areference signal sequence to the relevant layer of each rank based onn_(DMRS) ⁽²⁾ and a fixed offset may be used.

For example, assuming that the cyclic shift value of a DMRS sequence fora first layer (hereinafter referred to as a first layer cyclic shift) isn_(DMRS) ⁽²⁾, the cyclic shift value of the DMRS sequence for a secondlayer (hereinafter referred to as a second layer cyclic shift) may bedetermined as (n_(DMRS) ⁽²⁾+offset) mod CS_(total). Next, the cyclicshift value of the DMRS sequence for a third layer (hereinafter referredto as a third layer cyclic shift) and the cyclic shift value of the DMRSsequence for a fourth layer (hereinafter referred to as a fourth layercyclic shift) may be determined as (n_(DMRS) ⁽²⁾+2*offset) modCS_(total) and (n_(DMRS) ⁽²⁾+3*offset) mod CS_(total), respectively.That is, the first layer cyclic shift to the fourth layer cyclic shiftare continuously allocated at constant intervals of the offset. n_(DMRS)⁽²⁾ may be determined by a cyclic shift field within the DCI format 0transmitted through the PDCCH as described above. CS_(total) is a totalnumber of cyclic shifts and may be any one of 6, 8 or 12. Furthermore,the offset may be any one of 1, 2, and 3.

Table 6 to Table 11 illustrate cyclic shift values according to n_(DMRS)⁽²⁾ and layer indices when the number of layers is 4. For example, inTable 6, if n_(DMRS) ⁽²⁾=9, the offset is 1, and CS_(total)=12, a firstlayer cyclic shift is n_(DMRS) ⁽²⁾=9, and a second layer cyclic shift is(n_(DMRS) ⁽²⁾+offset) mod CS_(total)=(9+1) mod 12=10. Likewise, a thirdlayer cyclic shift is (n_(DMRS) ⁽²⁾+offset) mod CS_(total)=(9+2) mod12=11, and a fourth layer cyclic shift is (n_(DMRS) ⁽²⁾+offset) modCS_(total)=(9+3) mod 12=0.

Table 6 is a case where the offset is 1.

Cyclic shift First layer Second layer Third layer Fourth layer fieldn_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shift cyclic shift 000 0 01 2 3 001 2 2 3 4 5 010 3 3 4 5 6 011 4 4 5 6 7 100 6 6 7 8 9 101 8 8 910 11 110 9 9 10 11 0 111 10 10 11 0 1

Table 7 is a case where the offset is 1.

Cyclic shift First layer Second layer Third layer Fourth layer fieldn_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shift cyclic shift 000 0 01 2 3 001 6 6 7 8 9 010 3 3 4 5 6 011 4 4 5 6 7 100 2 2 3 4 5 101 8 8 910 11 110 10 10 11 0 1 111 9 9 10 11 0

Table 8 is a case where the offset is 2.

Cyclic shift First layer Second layer Third layer Fourth layer fieldn_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shift cyclic shift 000 0 02 4 6 001 2 2 4 6 8 010 3 3 5 7 9 011 4 4 6 8 10 100 6 6 8 10 0 101 8 810 0 2 110 9 9 11 1 3 111 10 10 0 2 4

Table 9 is a case where the offset is 2.

Cyclic shift First layer Second layer Third layer Fourth layer fieldn_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shift cyclic shift 000 0 02 4 6 001 6 6 8 10 0 010 3 3 5 7 9 011 4 4 6 8 10 100 2 2 4 6 8 101 8 810 0 2 110 10 10 0 2 4 111 9 9 11 1 3

Table 10 is a case where the offset is 3.

Cyclic shift First layer Second layer Third layer Fourth layer fieldn_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shift cyclic shift 000 0 03 6 9 001 2 2 5 8 11 010 3 3 6 9 0 011 4 4 7 10 1 100 6 6 9 0 3 101 8 811 1 4 110 9 9 0 3 6 111 10 10 1 4 7

Table 11 is a case where the offset is 3.

Cyclic shift First layer Second layer Third layer Fourth layer fieldn_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shift cyclic shift 000 0 03 6 9 001 6 6 9 0 3 010 3 3 6 9 0 011 4 4 7 10 1 100 2 2 5 8 11 101 8 811 1 4 110 10 10 1 4 7 111 9 9 0 3 6

Alternatively, a method of continuously allocating the cyclic shiftvalues of the DMRS sequence for the relevant layers of each rank basedon n_(DMRS) ⁽²⁾ and the fixed offset, wherein a fixed offset is anoffset in the cyclic shift field within the DCI format 0 may be used. Acyclic shift index transmitted from a higher layer may correspond to acyclic shift field in a one-to-one way. The cyclic shift value of theDMRS sequence for each layer may be determined as n_(DMRS) ⁽²⁾corresponding to a cyclic shift field index, and the cyclic shift indexof the DMRS sequence for each layer has an offset having a constantinterval.

For example, assuming that a first layer cyclic shift is index (i), asecond layer cyclic shift may be determined as index {(i+offset) mod 8}.Next, a third layer cyclic shift and a fourth layer cyclic shift may bedetermined as index {(i+2*offset) mod 8} and index {(i+3*offset) mod 8},respectively. That is, the cyclic shift values of the DMRS sequence forthe first layer to the fourth layer may be determined as n_(DMRS) ⁽²⁾corresponding to cyclic shift indices to which offsets are allocated atconstant intervals. n_(DMRS) ⁽²⁾ may be determined by the cyclic shiftfield within the DCI format 0 transmitted through the PDCCH as describedabove. The offset may be any one of 1, 2, and 3.

Table 12 to Table 17 illustrate cyclic shift values according to cyclicshift indices and layer indices when the number of layers is 4. Forexample, in Table 12, if the cyclic shift index is 6 and the offset is1, a first layer cyclic shift is index (6)=9, and a second layer cyclicshift is index {(i+offset) mod 8}=index (6+1) mod 8}=index (7)=10.Likewise, a third layer cyclic shift is index {(i+2*offset) mod 8}=index(6+2) mod 8}=index (0)=0, and a fourth layer cyclic shift is index{(i+3*offset) mod 8}=index (6+3) mod 8}=index (1)=2.

Table 12 is a case where the offset is 1.

Cyclic shift Cyclic shift First layer Second layer Third layer Fourthlayer index field n_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shiftcyclic shift 0 000 0 0 2 3 4 1 001 2 2 3 4 6 2 010 3 3 4 6 8 3 011 4 4 68 9 4 100 6 6 8 9 10 5 101 8 8 9 10 0 6 110 9 9 10 0 2 7 111 10 10 0 2 3

Table 13 is a case where the offset is 1.

Cyclic shift Cyclic shift First layer Second layer Third layer Fourthlayer index field n_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shiftcyclic shift 0 000 0 0 2 3 4 1 001 6 6 8 9 10 2 010 3 3 4 6 8 3 011 4 46 8 9 4 100 2 2 3 4 6 5 101 8 8 9 10 0 6 110 10 10 0 2 3 7 111 9 9 10 02

Table 14 is a case where the offset is 2.

Cyclic shift Cyclic shift First layer Second layer Third layer Fourthlayer index field n_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shiftcyclic shift 0 000 0 0 3 6 9 1 001 2 2 4 8 10 2 010 3 3 6 9 0 3 011 4 48 10 2 4 100 6 6 9 0 3 5 101 8 8 10 2 4 6 110 9 9 0 3 6 7 111 10 10 2 48

Table 15 is a case where the offset is 2.

Cyclic shift Cyclic shift First layer Second layer Third layer Fourthlayer index field n_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shiftcyclic shift 0 000 0 0 3 6 9 1 001 6 6 9 0 3 2 010 3 3 6 9 0 3 011 4 4 810 2 4 100 2 2 4 8 10 5 101 8 8 10 2 4 6 110 10 10 2 4 8 7 111 9 9 0 3 6

Table 16 is a case where the offset is 3.

Cyclic shift Cyclic shift First layer Second layer Third layer Fourthlayer index field n_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shiftcyclic shift 0 000 0 0 4 9 2 1 001 2 2 6 10 3 2 010 3 3 8 0 4 3 011 4 49 2 6 4 100 6 6 10 3 8 5 101 8 8 0 4 9 6 110 9 9 2 6 10 7 111 10 10 3 80

Table 17 is a case where the offset is 3.

Cyclic shift Cyclic shift First layer Second layer Third layer Fourthlayer index field n_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shiftcyclic shift 0 000 0 0 4 9 2 1 001 6 6 10 3 8 2 010 3 3 8 0 4 3 011 4 49 2 6 4 100 2 2 6 10 3 5 101 8 8 0 4 9 6 110 10 10 3 8 0 7 111 9 9 2 610

Alternatively, a method of allocating cyclic shift values so that aninterval between the cyclic shift values of the DMRS sequences forrespective layers becomes a maximum in the transmission of a pluralityof layers may be used. Here, the cyclic shift value of the DMRS sequencefor each layer may be determined by the number of layers and CS_(total)that is a total number of possible cyclic shifts. CS_(total) may be anyone of 6, 8, and 12.

For example, assuming that CS_(total)=12 and the number of layers is 2,when a first layer cyclic shift and a second layer cyclic shift areallocated at an interval of 6, an interval between the cyclic shiftvalues become a maximum. That is, the first layer cyclic shift and thesecond layer cyclic shift may be any one of {0,6}, {1,7}, {2,8}, {3,9},{4,10}, {5,11}, {6,0}, {7,1}, {8,2}, {9,3}, {10,4}, and {11,5}.Likewise, if the number of layers is 3, an interval between the cyclicshifts of the DMRS sequences for respective layers may be 4. If thenumber of layers is 4, an interval between the cyclic shifts of the DMRSsequences for respective layers may be 3. This may be represented byEquation 15.

$n_{DMRS\_ k}^{(2)} = {\{ {n_{DMRS}^{(2)} + {\frac{{CS}_{total}}{{the}\mspace{14mu} {total}\mspace{14mu} \# \mspace{14mu} {of}\mspace{14mu} {transmission}\mspace{14mu} {rank}\mspace{14mu} ( {{or}\mspace{14mu} {layer}} )} \cdot ( {k - 1} )}} \} {mod}\mspace{14mu} {CS}_{total}}$

k is a layer index, and N_(DMRS) _(—) _(k) ⁽²⁾ is the cyclic shift valueof a reference signal sequence for a layer having an index k.

If the number of layers is 2 and CS_(total)=12 in Equation 15, Equation16 may be obtained.

$\mspace{20mu} {{n_{{DMRS\_}1}^{(2)} = n_{DMRS}^{(2)}},{n_{{DMRS\_}2}^{(2)} = {{\{ {n_{DMRS}^{(2)} + {\frac{{CS}_{total}}{{the}\mspace{14mu} {total}\mspace{14mu} \# \mspace{14mu} {of}\mspace{14mu} {transmission}\mspace{14mu} {rank}\mspace{14mu} ( {{or}\mspace{14mu} {layer}} )} \cdot ( {k - 1} )}} \} {mod}\; {CS}_{total}} = {{\{ {n_{DMRS}^{(2)} + {\frac{12}{2} \cdot ( {2 - 1} )}} \} {mod}\; 12} = {\{ {n_{DMRS}^{(2)} + 6} \} {mod}\; 12}}}}}$

Table 18 is an example of cyclic shift values according to n_(DMRS) ⁽²⁾of Equation 16 and layer indices.

Cyclic shift First layer Second layer field n_(DMRS) ⁽²⁾ cyclic shiftcyclic shift 000 0 0 6 001 2 2 8 010 3 3 9 011 4 4 10 100 6 6 0 101 8 82 110 9 9 3 111 10 10 4

Table 19 is another example of cyclic shift values according to n_(DMRS)⁽²⁾ of Equation 16 and layer indices.

Cyclic shift First layer Second layer field n_(DMRS) ⁽²⁾ cyclic shiftcyclic shift 000 0 0 6 001 6 6 0 010 3 3 9 011 4 4 10 100 2 2 8 101 8 82 110 10 10 4 111 9 9 3

If the number of layers is 3 and CS_(total)=12 in Equation 15, Equation17 may be obtained.

$\mspace{20mu} {{n_{{DMRS\_}1}^{(2)} = n_{DMRS}^{(2)}},{n_{DMRS\_ k}^{(2)} = {{\{ {n_{DMRS}^{(2)} + {\frac{{CS}_{total}}{{the}\mspace{14mu} {total}\mspace{14mu} \# \mspace{14mu} {of}\mspace{14mu} {transmission}\mspace{14mu} {rank}\mspace{14mu} ( {{or}\mspace{14mu} {layer}} )} \cdot ( {k - 1} )}} \} {mod}\; {CS}_{total}} = {\{ {n_{DMRS}^{(2)} + {4 \cdot ( {k - 1} )}} \} {mod}\; 12}}}}$

Table 20 is an example of cyclic shift values according to n_(DMRS) ⁽²⁾of Equation 17 and layer indices.

Cyclic shift First layer Second layer Third layer field n_(DMRS) ⁽²⁾cyclic shift cyclic shift cyclic shift 000 0 0 4 8 001 2 2 6 10 010 3 37 11 011 4 4 8 0 100 6 6 10 2 101 8 8 0 4 110 9 9 1 5 111 10 10 2 6

Table 21 is another example of cyclic shift values according to n_(DMRS)⁽²⁾ of Equation 17 and layer indices.

Cyclic shift First layer Second layer Third layer field n_(DMRS) ⁽²⁾cyclic shift cyclic shift cyclic shift 000 0 0 4 8 001 6 6 10 2 010 3 37 11 011 4 4 8 0 100 2 2 6 10 101 8 8 0 4 110 10 10 2 6 111 9 9 1 5

If the number of layers is 4 and CS_(total)=12 in Equation 15, Equation18 may be obtained.

$\mspace{20mu} {{n_{{DMRS\_}1}^{(2)} = n_{DMRS}^{(2)}},{n_{DMRS\_ k}^{(2)} = {{\{ {n_{DMRS}^{(2)} + {\frac{{CS}_{total}}{{the}\mspace{14mu} {total}\mspace{14mu} \# \mspace{14mu} {of}\mspace{14mu} {transmission}\mspace{14mu} {rank}\mspace{14mu} ( {{or}\mspace{14mu} {layer}} )} \cdot ( {k - 1} )}} \} {mod}\; {CS}_{total}} = {\{ {n_{DMRS}^{(2)} + {3 \cdot ( {k - 1} )}} \} {mod}\; 12}}}}$

Table 22 is an example of cyclic shift values according to n_(DMRS) ⁽²⁾of Equation 18 and layer indices.

Cyclic shift First layer Second layer Third layer Fourth layer fieldn_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shift cyclic shift 000 0 03 6 9 001 2 2 5 8 11 010 3 3 6 9 0 011 4 4 7 10 1 100 6 6 9 0 3 101 8 811 2 5 110 9 9 0 3 6 111 10 10 1 4 7

Table 23 is another example of cyclic shift values according to n_(DMRS)⁽²⁾ of Equation 18 and layer indices.

Cyclic shift First layer Second layer Third layer Fourth layer fieldn_(DMRS) ⁽²⁾ cyclic shift cyclic shift cyclic shift cyclic shift 0 0 3 69 9 6 6 9 0 3 11 3 3 6 9 0 0 4 4 7 10 1 1 2 2 5 8 11 3 8 8 11 2 5 5 1010 1 4 7 6 9 9 0 3 6 7

In the above embodiment, the method of allocating the cyclic shift valueof the DMRS sequence for each layer when the number of layers is pluralhas been described, but the present invention may be applied to a casewhere the number of rank is 1 (i.e., a case where a plurality of layersis transmitted according to a transmit diversity scheme). Accordingly,the proposed method of transmitting a reference signal may be applied tothe cyclic shift value of the DMRS sequence for each layer. Table 24shows the number of required cyclic shift values and types of relevanttransmit diversity schemes.

Number of required cyclic shift values Transmit diversity scheme 1Preceding vector switching CDD (cyclic delay diversity) AntennaSelection TSTD(Time Switched Transmit Diversity) Rank1 preceding 2 STBC(Space Time Block Code) SFBC (Space Frequency Block Code) STTC (SpaceTime Trellis Code) SFTC (Space Frequency Trellis Code) FSTD (FrequencySwitched Transmit Diversity) TSTD CDD STBC/SFBC/STTC/SFTC/FSTD/TDTD +CDD ORT (Orthogonal resource transmission) 4STBC/SFBC/STTC/SFTC/FSTD/TDTD + FSTD FSTD (Frequency Switched TransmitDiversity) TSTD CDD

The above method of transmitting a reference signal may be usedaccording to the transmit diversity schemes of Table 24.

Furthermore, in the embodiment, an example where the proposed method oftransmitting a reference signal is applied to a DMRS has been described.The proposed method may also be applied to an SRS. If an SRS istransmitted in a multi-antenna system, the above method of transmittinga reference signal may be used. The DMRS is based on n_(DMRS) ⁽²⁾indicated by the cyclic shift field of the DCI format 0, but the SRS maybe based on n_(SRS) ^(cs) transmitted to each UE by means of a higherlayer.

First, a method of continuously allocating the cyclic shift values of areference signal sequence to the relevant layers of each rank based onn_(SRS) ^(cs) and a fixed offset may be used.

For example, assuming that a first layer cyclic shift is n_(SRS) ^(cs),a second layer cyclic shift may be determined as (n_(SRS) ^(cs)+offset)mod CS_(total). Next, a third layer cyclic shift and a fourth layercyclic shift may be determined as (n_(SRS) ^(cs)+2*offset) modCS_(total) and (n_(SRS) ^(cs)+2*offset) mod CS_(total), respectively.That is, the first layer to the fourth layer cyclic shift arecontinuously allocated at a constant interval of an offset. CS_(total)is the total number of possible cyclic shifts and may be any one of 6,8, and 12. Furthermore, the offset may be any one of 1, 2, and 3.

Table 25 to Table 27 illustrate cyclic shift values according to nSRS^(cs) and layer indices when the number of layers is 4. For example,if n_(SRS) ^(cs)=6, the offset is 1, and CS_(total)=8 in Table 25, afirst layer cyclic shift is n_(SRS) ^(cs)=6, and a second layer cyclicshift is (n_(SRS) ^(cs)+offset) mod CS_(total)=(6+1) mod 8=7. Likewise,a third layer cyclic shift is (n_(SRS) ^(cs)+2*offset) modCS_(total)=(6+2) mod 8=0, and a fourth layer cyclic shift is (n_(SRS)^(cs)+3*offset) mod CS_(total)=(6+3) mod 8=1.

Table 25 is a case where the offset is 1.

First layer Second layer Third layer Fourth layer n_(SRS) ^(cs) cyclicshift cyclic shift cyclic shift cyclic shift 0 0 1 2 3 1 1 2 3 4 2 2 3 45 3 3 4 5 6 4 4 5 6 7 5 5 6 7 0 6 6 7 0 1 7 7 0 1 2

Table 26 is a case where the offset is 2.

First layer Second layer Third layer Fourth layer n_(SRS) ^(cs) cyclicshift cyclic shift cyclic shift cyclic shift 0 0 2 4 6 1 1 3 5 7 2 2 4 60 3 3 5 7 1 4 4 6 0 2 5 5 7 1 3 6 6 0 2 4 7 7 1 3 5

Table 27 is a case where the offset is 3.

First layer Second layer Third layer Fourth layer n_(SRS) ^(cs) cyclicshift cyclic shift cyclic shift cyclic shift 0 0 3 6 1 1 1 4 7 2 2 2 5 03 3 3 6 1 4 4 4 7 2 5 5 5 0 3 6 6 6 1 4 7 7 7 2 5 0

Alternatively, a method of continuously allocating the cyclic shiftvalue of a reference signal sequence for each layer based on n_(SRS)^(cs) and a fixed offset, wherein the fixed offset is an offset of anindex corresponding to n_(SRS) ^(cs) in a one-to-one way may be used. Acyclic shift index transmitted from a higher layer may correspond ton_(SRS) ^(cs) in a one-to-one way. The cyclic shift value of thereference signal sequence for each layer may be determined as n_(SRS)^(cs) corresponding to a cyclic shift field index, and the cyclic shiftindex of the reference signal sequence for each layer has an offsethaving a constant interval. Table 28 is an example of a correspondingrelationship between the cyclic shift index and n_(SRS) ^(cs).

Cyclic shift index N_(SRS) ^(cs) (case 1) N_(SRS) ^(cs) (case 2) N_(SRS)^(cs) (case 3) 0 0 0 0 1 1 2 6 2 2 3 3 3 3 4 4 4 4 6 2 5 5 8 8 6 6 9 107 7 10 9

For example, assuming that a first layer cyclic shift is an index (i), asecond layer cyclic shift may be determined as index {(i+offset) mod 8}.Next, a third layer cyclic shift and a fourth layer cyclic shift may bedetermined as index {(i+2*offset) mod 8} and index {(i+3*offset) mod 8},respectively. That is, the first layer to the fourth layer cyclic shiftmay be determined as n_(SRS) ^(cs) corresponding to a cyclic shift indexto which an offset is allocated at a constant interval. The offset maybe any one of 1, 2, and 3.

Furthermore, a method of allocating cyclic shift values so that aninterval between the cyclic shift values of reference signal sequencesfor respective layers becomes a maximum may be used. Here, the cyclicshift value of the reference signal sequence for each layer may bedetermined by the number of layers and CS_(total) that is a total numberof possible cyclic shifts. CS_(total) may be any one of 6, 8, and 12.

For example, assuming that CS_(total)=8 and the number of layers is 2,when a first layer cyclic shift and a second layer cyclic shift areallocated at an interval of 4, an interval between the cyclic shiftvalues becomes a maximum. That is, the first layer cyclic shift and thesecond layer cyclic shift may be any one of {0,4}, {1,5}, {2,6}, {3,7},{4,0}, {5,1}, {6,2}, and {7,3}. Likewise, if the number of layers is 4,an interval between the cyclic shifts of the reference signal sequencesfor respective layers may be 2. This may be represented by Equation 19.

$n_{SRS\_ k}^{cs} = {\{ {n_{SRS}^{cs} + {\frac{{CS}_{total}}{{the}\mspace{14mu} {total}\mspace{14mu} \# \mspace{14mu} {of}\mspace{14mu} {transmit}\mspace{14mu} {antenna}} \cdot ( {k - 1} )}} \} {mod}\; {CS}_{total}}$

Here, k is a layer index, and N_(SRS) _(—) _(k) ^(cs) is the cyclicshift value of an SRS sequence for the layer index k.

If the number of layers is 2 and CS_(total)=8 in Equation 19, Equation20 may be obtained.

$\mspace{20mu} {{n_{{SRS\_}1}^{cs} = n_{SRS}^{cs}},{n_{SRS\_ k}^{cs} = {\{ {n_{SRS}^{cs} + {\frac{{CS}_{total}}{{the}\mspace{14mu} {total}\mspace{14mu} \# \mspace{14mu} {of}\mspace{14mu} {transmit}\mspace{14mu} {antenna}} \cdot ( {k - 1} )}} \} {mod}\; {CS}_{total}}}}$$\mspace{20mu} \begin{matrix}{n_{{SRS\_}2}^{cs} = {\{ {n_{SRS}^{cs} + {\frac{8}{2} \cdot ( {2 - 1} )}} \} {mod}\; 8}} \\{= {\{ {n_{SRS}^{cs} + 4} \} {mod}\; 8}}\end{matrix}$

Table 29 is an example of cyclic shift values according to n_(SRS) ^(cs)of Equation 20 and layer indices.

First layer Second layer n_(SRS) ^(cs) cyclic shift cyclic shift 0 0 4 11 5 2 2 6 3 3 7 4 4 0 5 5 1 6 6 2 7 7 3

If the number of layers is 4 and CS_(total)=8 in Equation 19, Equation21 may be

$\mspace{20mu} {{n_{{SRS\_}1}^{cs} = n_{SRS}^{cs}},{n_{SRS\_ k}^{cs} = {\{ {n_{SRS}^{cs} + {\frac{{CS}_{total}}{{the}\mspace{14mu} {total}\mspace{14mu} \# \mspace{14mu} {of}\mspace{14mu} {transmit}\mspace{14mu} {antenna}} \cdot ( {k - 1} )}} \} {mod}\; {CS}_{total}}}}$$\mspace{20mu} \begin{matrix}{n_{{SRS\_}k}^{cs} = {\{ {n_{SRS}^{cs} + {\frac{8}{4} \cdot ( {k - 1} )}} \} {mod}\; 8}} \\{= {\{ {n_{SRS}^{cs} + {2 \cdot ( {k - 1} )}} \} {mod}\; 8}}\end{matrix}$

Table 30 is an example of cyclic shift values according to n_(SRS) ^(cs)of Equation 21 and layer indices.

First layer Second layer Third layer Fourth layer n_(SRS) ^(cs) cyclicshift cyclic shift cyclic shift cyclic shift 0 0 2 4 6 1 1 3 5 7 2 2 4 60 3 3 5 7 1 4 4 6 0 2 5 5 7 1 3 6 6 0 2 4 7 7 1 3 5

FIG. 14 is a block diagram of a UE in which the embodiments of thepresent invention are implemented.

The UE 900 includes a reference signal generation unit 910, an OFDMsymbol generation unit 920, and an RF unit 930. The reference signalgeneration unit 910 generates a plurality of reference signal sequencesto which different cyclic shift values are allocated. The OFDM symbolgeneration unit 920 is coupled to the reference signal generation unitand configured to generate an OFDM symbol to which the plurality ofreference signal sequences is mapped. The RF unit 930 is coupled to theOFDM symbol generation unit and configured to transmit the OFDM symbolto a BS through a plurality of antennas 990-1, . . . , 990-N. A cyclicshift value allocated to each of the reference signal sequences may bedetermined based on a parameter n indicated by a cyclic shift fieldtransmitted through a PDCCH. The cyclic shift value of the referencesignal sequence for each layer in Table 6 to Table 23, Table 25 to Table27, or Table 29 to Table 30 may be determined by the UE of FIG. 14.

The exemplary embodiments of the present invention may be implemented byhardware, software, or a combination thereof. The hardware may beimplemented by an application specific integrated circuit (ASIC),digital signal processing (DSP), a programmable logic device (PLD), afield programmable gate array (FPGA), a processor, a controller, amicroprocessor, other electronic units, or a combination thereof, all ofwhich are designed so as to perform the above-mentioned functions. Thesoftware may be implemented by a module performing the above-mentionedfunctions. The software may be stored in a memory unit and may beexecuted by a processor. The memory unit or a processor may adoptvarious units well-known to those skilled in the art.

In the above-mentioned exemplary embodiments, the methods are describedbased on the series of steps or the flow charts shown by a block, butthe exemplary embodiments of the present invention are not limited tothe order of the steps and any steps may be performed in order differentfrom the above-mentioned steps or simultaneously. In addition, a personskilled in the art to which the present invention pertains mayunderstand that steps shown in the flow chart are not exclusive andthus, may include other steps or one or more step of the flow chart maybe deleted without affecting the scope of the present invention.

The above-mentioned embodiments include examples of various aspects.Although all possible combinations showing various aspects are notdescribed, it may be appreciated by those skilled in the art that othercombinations may be made. Therefore, the present invention should beconstrued as including all other substitutions, alterations andmodifications belonging to the following claims.

1. A method of transmitting a reference signal in a multi-antennasystem, the method comprising: generating a plurality of referencesignal sequences to which different cyclic shift values are respectivelyallocated; generating an orthogonal frequency division multiplexing(OFDM) symbol to which the plurality of reference signal sequences ismapped; and transmitting the OFDM symbol to a base station through aplurality of antennas, wherein the each cyclic shift value allocated toeach of the plurality of reference signal sequences is determined basedon a parameter n indicated by a cyclic shift field transmitted through aphysical downlink control channel (PDCCH).
 2. The method of claim 1,wherein each of the plurality of reference signal sequences is areference signal sequence for a different layer.
 3. The method of claim1, wherein the each cyclic shift value allocated to each of theplurality of reference signal sequences is determined based on a valueindicated by a rank indicator (RI).
 4. The method of claim 1, whereinthe each cyclic shift value allocated to each of the plurality ofreference signal sequences is determined so that an interval between thecyclic shift values becomes a maximum based on the parameter n.
 5. Themethod of claim 4, wherein the each cyclic shift value allocated to eachof the plurality of reference signal sequences is determined by theEquation below,${n_{k} = {\{ {n + {\frac{{CS}_{total}}{{the}\mspace{14mu} {total}\mspace{14mu} \# \mspace{14mu} {of}\mspace{14mu} {transmission}\mspace{14mu} {rank}\mspace{14mu} ( {{or}\mspace{14mu} {layer}} )} \cdot ( {k - 1} )}} \} {mod}\; {CS}_{total}}},$where n_(k) is a cyclic shift value of a reference signal sequence for alayer having a layer index k, n is the parameter indicated by the cyclicshift field transmitted through the PDCCH, and CS_(total) is a totalnumber of possible cyclic shifts.
 6. The method of claim 5, wherein anumber of layers is one of 2, 3, and
 4. 7. The method of claim 5,wherein CS_(total) is one of 6, 8, and
 12. 8. The method of claim 1,wherein the each cyclic shift value allocated to each of the pluralityof reference signal sequences is determined at an interval of an offsetconstantly fixed based on the parameter n.
 9. The method of claim 8,wherein the each cyclic shift value allocated to each of the pluralityof reference signal sequences is determined by the Equation below,n _(k)=(n+(k−1)*offset) mod CS _(total), where n_(k) is a cyclic shiftvalue of a reference signal sequence for layer having a layer index k, nis the parameter indicated by the cyclic shift field transmitted throughthe PDCCH, and CS_(total) is a total number of possible cyclic shifts.10. The method of claim 1, wherein the each cyclic shift value allocatedto each of the plurality of reference signal sequences is transmitted bya higher layer based on the parameter n, and the each cyclic shift valueallocated to each of the plurality of reference signal sequences isdetermined by an offset of a cyclic shift index corresponding to theparameter n in a one-to-one way.
 11. The method of claim 1, wherein anumber of the plurality of antennas is one of 2, 3, and
 4. 12. Themethod of claim 1, wherein the OFDM symbol to which the plurality ofreference signal sequences is mapped is a fourth OFDM symbol (OFDMsymbol index 3) in a slot including 7 OFDM.
 13. The method of claim 1,wherein the OFDM symbol to which the plurality of reference signalsequences is mapped is a third OFDM symbol (OFDM symbol index 2) in aslot including 6 OFDM.
 14. An apparatus for transmitting a referencesignal in a multi-antenna system, the apparatus comprising: a referencesignal generation unit configured for generating a plurality ofreference signal sequences to which different cyclic shift values arerespectively allocated; an orthogonal frequency division multiplexing(OFDM) symbol generation unit coupled to the reference signal generationunit and configured for generating an OFDM symbol to which the pluralityof reference signal sequences is mapped; and a radio frequency (RF) unitcoupled to the OFDM symbol generation unit and configured fortransmitting the OFDM symbol to a base station through a plurality ofantennas, wherein the each cyclic shift value allocated to each of theplurality of reference signal sequences is determined based on aparameter n indicated by a cyclic shift field transmitted through aphysical downlink control channel (PDCCH).
 15. The apparatus of claim14, wherein the each cyclic shift value allocated to each of theplurality of reference signal sequences is determined based on a valueindicated by a rank indicator (RI).